DG7YBN / Phasing & Matching Lines & Baluns
  Last Update Feb 17th 2018




.......


     

Coax Cable Transformers

Coaxial Transformers are of relatively narrow -3 dB bandwidth.

Quarter Wave Line tranformation ratio Z calc.
Quarter Wave Line 12.5 ohms to 50 ohms
Quarter Wave Line 28 ohms to 50 ohms
Quarter Wave Line 200 ohms to 50 ohms
Twelfth Wave Line 50 ohms to 75 ohms

Broadband Transformers

For matching TV or LTE Antennas a broadband transformer that covers
several 10 MHz or even the whole UHF TV band is to be preferred.

Ferrite Transformer
PCB Transformer

Half Wave Balun for Folded Dipoles

Half Wave Balun 200 ohms to 50 ohms
What to avoid when feeding the Folded DE

Odd multiples of λ/4

What about odd multiples of λ/4

Feeding stacked Antennas with Coax

Feeding 2 x 25 ohms
Feeding 2 x 50 ohm
Feeding 4 x 50 ohms

Connecting Array Dipoles in Phase

Feeding 4 Folded Dipoles in Phase
Feeding 4 Straight Split Dipoles in Phase
Feeding a Vertical 4 Yagi Stack in Phase





Preface: How to trim coax to length & why v-factor is depending on frequency

  Attenzione!

It is understood that a length of coax cable needs to be shortened using its velocity factor
if we want to cut a resonate length. A waves speed in a medium is described as

... or multiplied by 100 as % of speed of light.

According IEC 60250 the dielectrical constant εr of (natural) PTFE is 2.1, measured at 1 MHz equalling v = 0.690 = 69%. However Radio Amateurs mostly use v = 0.7... 0.71 so that the calculated length of a 144 MHz Quarter Wave Line is around 369 mm.
But have you ever measured the resonance frequency what you have cut? At VHF and above you will probably be surprised to find your stub being some 5...10% too low in resonance frequency. This is due to εr and v-factor being specified at a much lower frequency and plastics dielectrical properties are frequency depending to a certian extend.

The full story is that plastics hold a so called Dynamic Dielectrical Constant:

    M. Bonnet, Kunststoffe in der Ingenieuranwendung, Vieweg + Teubner, Wiesbaden 2009, pg. 73
    Chapter 1.7.1.3 Dynamic Dielectrical Constant and Dielectrical Loss

    My translation from original German text:

    'In an alternating electrical field the electrical dipoles [of the plastic]
    are forced to oscillate with frequency ν of the alternating field. Molecules
    with orientation polarisation are hereby constantly forced to alter their alignment
    in the volume. This leads to relaxation damping.'

It is said relaxation damping that degrades the dielectrical constant with increasing frequency, which lowers the wave speed in the plastic. That makes our velocity factor drop - and so needs our coax stubs length at VHF and above. Eventually measuring and tuning in the exact length of your VHF/UHF coax balun or quarter wave lines is a must if it shall be precise. Not to mention the influence of all connecting open coax ends.


  How to measure a coax lines resonance frequency

Any quarter lambda of coax line acts as a resonate circuit. Any odd multiple length does too. A λ/2 balun line can be measured as quarter lambda at the resulting frequency. On VHF/UHF the true resonate length will be some 5 to 7% shorter than calculated.



Using the Dipmeter

Join one sides split ends, take a dipmeter and go ... . Most dipmeters frequency readings are not as accurate as we would like to have it. So I run my station RX on 144.200 MHz and listen for the "dip" to come by. You might add a mark to your dipmeters scale then.

     



Using a Network Analyser

If your Network Analyser can perform transmission mode you have an quite accurate instrument at hand. Basically the S21 network parameter is same as transmission mode.

Principle

Inductive coupling

 

Capacitive coupling


If you are a newbie using analysers you may read my 'Intro to Analysers' - here





A piece of H2010 trimmed to resonate at 144.1 and harmonics (with OBZOR / Planar TR1300 VNA)


And here is the piece of coax the above plot belongs to ... it is the very new H2010 coax cable


That line is ment to perform in the prototype of my 432 MHz GTV 70-19m.

As the H2010 is very low loss (8.68 dB per 100 m on 432 MHz), UV resistent, has a flexible core, water rejecting PE foam dielectricum, and handles almost 1 kW on 432 MHz I think it is the right choice for a 70 cm high grade Yagi.

A test length was kindly provided by Kabel Kusch - TNX!

This length is a 1/4 λ on 144 MHz and 3 x 1/4 λ on 432 MHz. Just as the above VNA plot shows. Using odd multiples on 3rd harmonic frequency does not change anything since we can look upon this length as a single Quarter Wave Line followed by a halfwave length - with does not change anything on the impedance - apart from the little loss it brings.

So that this line works in a 144 MHz as well as in a 432 MHz Yagi as a symmetrising 50 to 50 ohm member ... the better so when a ferrite core is added close to the driven element feed point.



In transmission mode the analyser will show the transmisson properties of whatever is fitted between the DUT and DET ports. If we use two coax lines with coils at the ends and place the short circuited end of the to be measured stub between these coupling coils we find the transmisson path being disturbed by the stub where it is resonate. See the little peak in image below? That is our frequency reading. Loose coupling, just enough to notice a tiny wobble is best since it will least influence the resonance of the stub.

From theory to real world:

Photos on courtesy of Erwin, DK5EW who tested this himself   ... (inductive coupling, VNA side coax shortened, far end open)

   

These measurement coaxes might be a little short for use on 432 MHz. Not to create build in resonances or quarterwave lines in there!

DK5EW measures 144.40 MHz for 342 mm of RG-142 PFTE coax; I found 345 mm for 144.20 MHz for same RG-142:


A coupling plate made out of a defective coax relay at DG7YBN (capacitive coupling); VNA side end open, other shortened

move stubs core close in between plates for measuring ...

The commonly used v-factor (for 1 MHz) has it with 369 mm - which leaves you with a quarter wave coax perfectly cut ... for around 133 MHz instead. If you install that likewise as 2 x 75 ohms into a Yagi it does not take rocket science to find out why you might think you do not need a BC on that build. For any conventional Yagi-Uda it is the excess length of that matching coax that will add to the DE and make it appear longer and compensate for the falling short elements. Which works out for the respondig frequency but surely not for the pattern.

Inductive Coupling Bridge to VNA by DL2VL (tnx Jörg)

VNA Plot of a Quarter Wave line by DL2VL (S11 param: Input Reflection : Return Loss in dB)






Measuring a 1/4 λ line as a stub, performed by PA2CV, Alex:

Alex produced a measurement bridge from two lengths of coax with SMA connectors, calibrated the bridge without the stub, soldered the Quarterwave line to the SMA connection and plotted the Return Loss (S11), see below. A fair methode that overcomes the challenges of the tricky capacitive or inductive coupling the transmission mode methode holds.

432 MHz 1/4 λ line from RG-142

Plotted Return Loss (S11) of the trimmed stub









Lambda/4 - Common Mode Choke / Sleeve Balun for GTV 70-25, performed by DF7KB, Wolf:

Wolf has connected 2 SMA bushings with a 50 ohms stripline:

"The frequency response is almost flat (to above 1500 MHz). I connected the just produced sleeve balun. Whcih results in a measurement depth of 30 - 40 dB."

Fig. 1 shows four coaxial Lambda / 4 sleeve baluns. Their geometry is:
Core Rod: Diameter = 5 mm; Length = 141,5 mm
Outer Tube: Diameter 14 / 12 mm; Length = 142 mm
The core rod is centered by a PFTE ring (thickness 2 mm). The pin of the N socket
centers on the other side.


"Fig. 1 also shows the "aluminium provisional boom" and the coupling with measurement coaxes to the VNA
This coupling consists of a 50 ohms strpline which ends into two SMA bushings.
The frequency slope of this probe is almost linear up to 1500 MHz.
The core of the sleeve balun is soldered to the stripline, the outer conductor is
connected to the gnd of the stripline.
"

Fig. 2 shows the test setup. Provisional boom and ferrite core do shift resonance of the sleeve balun up to a total of 500 kHz and thus should be incorporated when tuning.


Measurement Bench: sleeve on substitute boom for best precision in measuring
• Shift of resonance spot with boom: approx. 100 kHz
• Shift of resonance spot with ferrite: approx. 200 kHz

Below: coupling inductances for inductive coupling of stubs for plotting in Transmission Mode

Fig. 3 shows the resonace of the sleeve balun

Fig. 4 Such a sleeve balun can of coarse alos be used on its 3/4 Lambda resonance

Fig. 5 That sleeve balun mounted onto a GTV 70-25


Setup, text und photos kindly provided by Wolf, DF7KB








Measuring a 1/4 λ line cross checking results inductive vs. stripline bridge coupling by John, ZS6JON

John wanted to cross check between both methods
• the inductive coupling of a stub als a 1/4 wl ciruit in transmission mode
• the stripline bridge as real stub in a transmission line.

First the classical 1/4 wl ciruit in transmission mode phase change plot:

144.3 MHz x 3 = 432.9 MHz

Second the stripline setup

432.1 MHz

With ferrite core as close as can towards the split end

With ferrite core at 5 mm down from the split end

Plot with ferrite 5 mm off: 432.78 MHz now


Note that for very accurate measurements details as
• position of the ferrite core
• a substitue boom and height of coax line above that
will make the difference on the few 100 kHz







Measuring a 1/4 λ line for the 4 m band by John, ZS6JON

Photo and plot on courtesy of John, ZS6JON. tnx





• Find sample VNA plots of a full Yagi with right and wrong lengths of matching coax on Symmetrising Website


Flag Counter





Coax Transformers



How to determine the needed Z for a wanted Quarter Wave Lines tranformation ratio

   



Some applied examples

1.  From 50 ohms feedline to 12.5 ohms Yagi with straight split DE?
    Z = sqrt ( 50 ohms x 12.5 ohms) = 25 ohms
    This we can produce by using two 50 ohms Quarter Wave Lines in parallel
	
2.  From 50 ohms feedline to 28 ohms Yagi with straight split DE?
    Z = sqrt ( 50 ohms  x  28 ohms) = 37.4 ohms
    This we nearly can produce by using two 75 ohms Quarter Wave Lines in parallel

3.  And finally the trivial case:
    From 50 ohms feedline to 50 ohms Yagi with straight split DE?
    Z = sqrt ( 50 ohms x 50 ohms) = 50 ohms



How to transform from 50 ohms to 12.5 ohms using parallel Quarter Wave Lines





How to transform from 50 ohms to 28 ohms using parallel Quarter Wave Lines (aka DK7ZB - Match)





How to transform from 50 ohms to 200 ohms using parallel Quarter Wave Lines // corrected 2014-09-23, tnx DH1LM,
who showed me that the old sketch was wrong. Hopefully this one does ...

Using Quarter Wave Lines this way works as a series collection actually, Z is 100 ohms, Za = 50 ohms, Zb = 200 ohms



How to transform from 50 ohms to 75 ohms using parallel Twelfth Wave Lines







How produce Ferrite RF Transformers for various impedances transformation ratios

• Ferrite Transformer

Image shows a 1:1 transformer as blue and black wires windings
ratio is 1:1. This one is for Shortwave use. For VHF / UHF dimensions must be much smaller.

Windings N1/N2 ratio by square is transformation ratio for impedance:

Example: Za = 50 ohms, Zb = 200 ohms ...
Na = 6 wdg; Nb = 12 wdg => Na/Nb = 6/12 = 0.5
Transformation ratio = (Na/Nb)xy2 = 0.25 = 1/4 or 1:4
200 ohms x 0.25 = 50 ohms

• Balun Transformer

The Balun transformer is a two-in-one device:
The transformation ratio is same as described above, but now the 50 ohms side is unbalanced (coax feed)
while the 200 ohms side is balanced or symmetrical.

An often seeked for transformation ratio might be 50 to 75 ohms.
This could be acheived using 6 and 9 wdg. respectively 6 + 3 wdg on the Balun Transformer.

• What about the size of the ferrite then?

For any receiving purpose it may be very small. Same to the wire diameters. A tiny ferrite bead equipped with 0.12 mm or so enameled copper wire will do for most purposes. For handling transmitting power or limits issuing intermodulation there is one rule: The ferrite must not saturate. Big is beautiful and size does matter here. Unlike with applications for short wave where ferrite baluns in transmitting antennas are widely used we have only few data and less working ferrite materials when we talk VHF / UHF applications. A rule of thumbs is .. it must not heat up much, it shall not get hot of very warm during transmitting. Having large size ferrites and wires wrapped around is in contradiction to the need for shortest wires on VHF / UHF. That is why we find receiving purpose small ferrite bead based transformers often, but power handling transmitting transformer very seldom here.

Real dimensions: using very small double hole ferrites in a 144 MHz RX frontend

they do not need to be as tiny as that, but to give an impression ...



However here is a little table holding some suitable types, makes and sizes for VHF / UHF transmitting purpose ferrite transformers

Size Amidon T37 or T50, inner diam. = 5.21 / 7.70 mm fit RG58 and RG142 B/U Teflon coax.
Size Amidon T80, inner diam. = 12.60 mm fits RG213 coax, Aircell ...
Code T50-0 (color code: brown) covers 50-300 MHz

Material 43 is for blocking VHF/UHF frequencies

A good choice are the following cores:

FT 50 B-43 inner diam. 7.9 mm, outer diam 12.7 mm, length 12.7 mm (approx EUR 3 pp.)
FB-43-5621 inner diam. 6.4 mm, outer diam. 14.3 mm, length 28.6 mm
FB 43-1020 inner diam. 12.7 mm, outer diam. 25.4 mm, length 28.2 mm







A commerially made broad band Transformer to match 75 ohms feedline coax to a 300 ohms UHF TV antenna

PCB with inductances.
Designing something like this is rather complex and usually done using an 'EM' software like Sonnet EM, FEKO, ADS ... . So I just show an example. For those who want to dig themselfs into the topic: There are free, limited in size of analysed object versions like 'Sonnet EM Lite' available.


For an etched on PCB solution for 70 cm Amateur Radio Band that does 50 to 28 ohms see here







How to transform from 50 ohms to 200 ohms to feed a Folded Dipole as Driven Element

The transformation ratio of a Half Wave "Diversion" Line is 1:4.




What to avoid feeding a Folded DE

Do not attach the feeding coax in a way as shown above so that the coax loop forms anything close to Quarter Wave Line in series to the Balun. Being close to Quarter Lambda it might interfere seriously with the Balun and you end up with bad VSWR on a nice antenna probably. Most attention must be paid if the Balun side of the FD is free floating i.e. not connected to gnd respectively boom.

Tape it to the boom right from the connector or box on, or leave it hanging for much longer than λ/4 x v-factor.







Note: Any odd multiple of λ/4 such as 5/4 λ or 7/4 λ will transform exactly as the sole λ/4 line. Why so?
Because a half wave line does not change anything, apart from losses. Any odd number of λ/4 can be seen as a number of half wave lines plus a single λ/4 wave line.

Practical hint: I used a quality coaxial 432 MHz 4 x power splitter for joining four 1296 MHz Yagis on serveral contest occasions with good success.
Same would apply to 144 MHz splitters to use on 432 Mhz and so forth. Any tripple frequency ... just mind connecting bushings pins inductances or coax pigtails that have more impact on that tripple frequency.




Feeding stacked Antennas with Coax



How to feed two 25 ohm Antennas from 50 ohm coax





How to feed two 50 ohm Antennas from 50 ohm coax

  Attenzione! Building this 75 ohms coaxial cable splitters with 50 ohms T-connectors will not satisfy. A small length of 50 ohms instead of 75 ohms just before the sum point is an impedance discontinuity serious enough to prevent the VSWR from being better than appox. 1:1.2



How to feed four 50 ohm Antennas from 50 ohm coax

A conventient way to feed a 4 Yagi stack. 4 x 50 ohms any length means any length but all four of same length.



How to feed four 50 ohm Antennas in typical H-configuration from 50 ohm coax in style

A classical 4 Yagi stack may be fed and phased using 50 ohms coax efficiently when using odd multiples of λ/4 like 5/4 λ for making the horizontal phasing lines. An example: At a given stacking distance of 3.0 m the 5/4 λ equals 5 x 0.34 m = 1.7 m roughly on 144 MHz whe taking the v-factor for PE coax into account. That makes it 1.7 m to the left plus 1.7 m to the right. Enough to bridge over the two H-frame tubes.







How to get four Folded Dipoles fed in phase

It is understood that all feeding coaxes must be of similar length and impedances must be transformed as shown above or using a Power Splitter

• All shields are to be connected on same side
• All Folded Dipoles are facing upwards

... which in typical H-frame 4 bay configuration involves turning the struts of the lower pair upside down while elements and Dipole stay as on the upper pair. Or simply put: all dipole boxes or Matches face down.







How to get four Straight Split Dipoles fed in phase

It is understood that all feeding coaxes must be of similar length and impedances must be transformed as shown above or using a Power Splitter

• All shields are to be connected on same side








How to get a vertical 4 Yagi stack fed in phase

In General:

It is understood that all feeding coaxes (1,2,3,4) must be of similar length and impedances must be transformed as shown above or using a Power Splitter

Specificly:

Using similar lengths for all four feeding coaxes needs somehow winding up # 2 and 3. We find a remedy here using a length of minus full 360 degr. for the inner coaxes # 2, 3. As 360 degr. or even multiples of that do not change anything according feeding phase. With a lag of n x 360 degr. we are just at the same point on the sinus we find on the outer Yagis. Which in practise means we are feeding all dipoles in phase.

An example: 360 degr. is just 1.0 wavelength, multiplied with real velocity factor of coax to be used at designated frequency. Likewise v = 0.82 of some foam insulated coax on 144.1 MHz (2.080 m) makes 360 degr. of runtime on coax be equivalent to a length of 1.706 m Simply put: coaxes # 2, 3 can be 1.706 m shorter than the coaxes # 1, 4 feeding the outer dipoles.

• All shields are to be connected on same side






73, Hartmut, DG7YBN


Flag Counter